Pulse output circuit, shift register, and display device

ABSTRACT

A circuit is provided which is constituted by TFTs of one conductivity type, and which is capable of outputting signals of a normal amplitude. When an input clock signal CK 1  becomes a high level, each of TFTs ( 101, 103 ) is turned on to settle at a low level the potential at a signal output section (Out). A pulse is then input to a signal input section (In) and becomes high level. The gate potential of TFT ( 102 ) is increased to (VDD−V thN) and the gate is floated. TFT ( 102 ) is thus turned on. Then CK 1  becomes low level and each of TFTs ( 101, 103 ) is turned off. Simultaneously, CK 3  becomes high level and the potential at the signal output section is increased. Simultaneously, the potential at the gate of TFT ( 102 ) is increased to a level equal to or higher than (VDD+V thN) by the function of capacitor ( 104 ), so that the high level appearing at the signal output section (Out) becomes equal to VDD. When SP becomes low level; CK 3  becomes low level; and CK 1  becomes high level, the potential at the signal output section (Out) becomes low level again.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to a pulse output circuit, a shiftregister and a display device. Note that in this specification, displaydevices include a liquid crystal display device using a liquid crystaldisplay element as a pixel, and a self-luminous display device using aself-luminous element, e.g., an electroluminescent (EL) element. Drivercircuits for a display device are circuits which perform processing fordisplaying an image by inputting image signals to pixels arranged in thedisplay device, and which include pulse output circuits, e.g., a shiftregister and an inverter, and amplifier circuits.

2. Description of the Related Art

In recent years, display devices having a semiconductor thin film formedon an insulating substrate such as a glass substrate, particularlyactive matrix display devices using thin film transistors (TFTs) havebecome widely available and have been used in various products. Anactive matrix display device using TFTs has several hundred thousand toseveral million pixels arranged in a matrix form and displays an imageby controlling charge on each of the pixels by means of a TFT providedin the pixel.

Techniques relating to polysilicon TFTs have recently been developedwhich comprise forming driver circuits on a substrate on the peripheryof a pixel portion by using TFTs simultaneously with the formation ofpixel TFTs constituting pixels. Such techniques have contributed to thedevelopment of display devices reduced in size and in power consumption.Also, such display devices have become indispensable to display unitsfor mobile information terminals which have found application in anincreasing number of application areas in recent years.

Ordinarily, a complementary metal-oxide-semiconductor (CMOS) circuitusing a combination of an n-channel TFT and a p-channel TFT is used as acircuit constituting driver circuits for display devices. A shiftregister will be described as an example of this CMOS circuit withreference to FIGS. 11A, 11B, and 11C. A section in a frame 1100indicated by a dotted line is a circuit forming one stage for outputtinga pulse. Only three of the pulse output stages of the shift register areshown in FIG. 11A. Each circuit forming one stage is constituted byclocked inverters 1101 and 1103, and an inverter 1102. FIG. 11B showsdetails of the circuit configuration. Referring to FIG. 11B, TFTs 1104to 1107 constitute a clocked inverter 1101, TFTs 1108 and 1109constitute a clocked inverter 1102, and TFTs 1110 to 1113 constitute aclocked inverter 1103.

Each of the TFTs constituting the circuit has three electrodes: a gateelectrode, a source electrode, and a drain electrode. However, thesource region and the drain region cannot be discriminated from eachother because of a structural characteristic of the TFT. In ordinaryCMOS circuits, one of the source and drain regions of the n-channel TFTat a lower potential is used as a source electrode, while the other at ahigher potential is used as a drain electrode. Also, one of the sourceand drain regions of the p-channel TFT at a higher potential is used asa source electrode, while the other at a lower potential is used as adrain electrode. In the description of the connection of TFTs in thisspecification, the source and drain electrodes are referred to as afirst electrode and a second electrode, respectively, or as a secondelectrode and a first electrode, respectively, to avoid confusing themone with the other.

The operation of the circuit will be described. In the followingdescription of the operation of TFTs, a conducting state when a channelis formed between impurity regions by application of a potential to thegate electrode is represented by “ON”, and a non-conducting state whenthe impurity region channel is not formed is represented by “OFF”.

Referring to FIGS. 11A and 11B and FIG. 11C, which is a timing chart, aclock signal (hereinafter referred to as “CK”) and an inverted clocksignal (hereinafter referred to as “CKB”) are respectively input to theTFTs 1107 and 1104. A start pulse (hereinafter referred to as “SP”) isinput to the TFTs 1105 and 1106. When CK is high level; CKB is lowlevel; and SP is high level, each of the TFTs 1106 and 1107 is ON andlow level is output to be input to the inverter 1102 constituted by theTFTs 1108 and 1109. The inverter 1102 inverts the input low level andoutputs high level through an output node (SRout 1). Thereafter, CKbecomes low level and CKB becomes high level, while SP is high level.Then, a holding operation by means of a loop formed by the inverter 1102and the clocked inverter 1103 is performed. Outputting high levelthrough the output node is thus continued. CK and CKB then become highlevel and low level, respectively, and the clocked inverter 1101 againperforms the write operation. Low level is thus output through theoutput node since SP has already become low level. Subsequently, when CKand CKB become low level and high level, respectively, the holdingoperation is again performed. Low level output from the output node atthis time is held in the loop formed by the inverter 1102 and theclocked inverter 1103.

The operation of one stage is thus performed. In the next stage, theconnections with respect to CK and CKB are reversed and the sameoperation as described above is performed according to the reversedpolarity of the clock signal. The same operation is repeated accordingto the polarity of the clock signal alternately changed. Sampling pulsesare thus output successively, as shown in FIG. 11C.

A feature of the CMOS circuit should be mentioned which resides inlimiting power consumed by the entire circuit. That is, a current flowsonly at a moment when a change in logic state (from high level to lowlevel or from low level to high level) occurs and no current flows whena logic state is maintained (although in actuality a small leak currentflows).

The demand for display devices using liquid crystals or self-luminouselements is growing rapidly with the development of mobile electronicdevices reduced in size and weight. However, it is difficult toeffectively reduce the manufacturing cost of such display devices byimproving the yield, etc. It is naturally conceivable that the demandwill further grow rapidly. Therefore, it is desirable to supply displaydevices at a reduced cost.

A method of forming an active layer pattern, a wiring pattern, etc., byperforming exposure and etching using a plurality of photomasks isordinarily used as a method of fabricating a driver circuit on aninsulator. Since the number of manufacturing steps is a dominant factorin determining the manufacturing cost, a manufacturing method using areduced number of manufacturing steps is ideal for manufacture of drivercircuits. If driver circuits can be formed by using TFTs of only one oftwo conductivity types, i.e., the n-channel or p-channel type, insteadof being formed of CMOS circuits, part of the ion doping process can beremoved and the number of photomasks can be reduced.

FIG. 9A illustrates a CMOS inverter (I) ordinarily used, and inverters(II) and (III) formed by using only TFTs of one polarity or by usingonly one TFT. The inverter (II) has a TFT used as a load. The inverter(III) has a resistor used as a load. The operation of each inverter willbe described.

FIG. 9B shows the waveform of a signal input to each inverter. The inputsignal amplitude is low level/high level=VSS/VDD (VSS<VDD). It isassumed that VSS=0 V.

The operation of the circuit will be described. To describe theoperation simply and explicitly, it is assumed here that the thresholdvoltages of n-channel TFTs are equal to each other and are representedby V thN across the board, and that, similarly, the threshold voltage ofa p-channel TFT is represented by a constant value V thP.

When a signal such as shown in FIG. 9B is input to the CMOS inverter,and when the potential of the input signal is high level, the p-channelTFT 901 is OFF and the N-channel TFT 902 is ON. The resulting potentialat the output node is low level. Conversely, when the potential of theinput signal is low level, the p-channel TFT 901 is ON and the N-channelTFT 902 is OFF. The resulting potential at the output node is high level(FIG. 9C).

The operation of the inverter (I) using a TFT as a load will next bedescribed with respect to a case where a signal such as shown in FIG. 9Bis input. When the input signal is low level, the n-channel TFT 904 isOFF. The load TFT 903 is operating in a saturated state. As a result,the potential at the output node is pulled up toward a high level. Onthe other hand, when the input signal is high level, the n-channel TFT904 is ON. The potential at the output node is pulled down toward a lowlevel if the current capacity of the n-channel TFT 904 is sufficientlylarger than the current capacity of the load TFT 903.

In the inverter (III) using a resistor as a load, the ON resistance ofthe n-channel TFT 906 is set to a value sufficiently smaller than theresistance value of a load resistor 905. In this inverter, therefore,when the input signal is high level, the n-channel TFT 906 is ON and thepotential at the output node is pulled down toward a low level. When theinput signal is low level, the n-channel TFT 906 is OFF and thepotential at the output node is pulled down toward a high level.

However there is a problem described below with each of the inverterusing a TFT as a load and the inverter using a resistor as a load. FIG.9D shows the waveform of the output from the inverter using the TFT 903as a load. When the output is high level, the potential of the output islower than VDD by an amount indicated by 907. If in the load TFT 903 theterminal on the output node side is a source while the terminal on thepower supply VDD side is a drain, the potential at the gate electrode isVDD, since the gate electrode and the drain region are connected to eachother. The condition for maintaining the load TFT in the ON state is(TFT 903 gate-source voltage>V thN). Therefore the highest level towhich the potential at the output node can be increased is (VDD−V thN).That is, the amount 907 is equal to V thN. Further, when the output islow level, the potential of the output is higher than VSS by an amountindicated by 908, depending on the ratio of the current capacities ofthe load TFT 903 and the n-channel TFT 904. To bring the outputpotential sufficiently close to VSS, it is necessary to sufficientlyincrease the current capacity of the n-channel TFT 904 relative to thatof the load TFT 903. Similarly, referring to FIG. 9E showing thewaveform of the output from the inverter using the resistor 905 as aload, the potential of the output is higher by an amount indicated by909, depending on the ratio of the resistance value of the load resistor905 and the ON resistance of the n-channel TFT 906. That is, in use ofthe above-described inverter formed by using only one TFT or only TFTsof one polarity, the amplitude of the output signal is attenuatedrelative to the amplitude of the input signal.

SUMMARY OF THE INVENTION

In view of the above-described problem, an object of the presentinvention is to provide a pulse output circuit which is formed by usingonly TFTs of one polarity, which can therefore be fabricated at a lowcost by performing a reduced number of manufacturing steps, and fromwhich an output can be obtained without being attenuated in amplitude,and a shift register using the output circuit.

Conditions for ensuring that the amplitude of the output signal has anormal value of low level/high level=VSS/VDD in the inverter shown in(II) of FIG. 9A as an inverter using a TFT as a load will be discussed.First, in a circuit such as shown in FIG. 10A, when the output signalpotential becomes low level, a state in which the resistance betweenpower supply VSS and output node (Out) is sufficiently small relative tothe resistance between power supply VDD and output node (Out) sufficesfor bringing the potential of the output signal sufficiently close toVSS. That is, maintaining an n-channel TFT 1001 in the OFF state duringthe time period when an n-channel TFT 1002 is ON suffices.

Secondly when the output signal potential becomes high level, a state inwhich the absolute value of the gate-source voltage of the n-channel TFT1002 is always higher than V thN and the TFT 1001 is reliably maintainedin the OFF state suffices for making the potential of the output signalequal to VDD. That is, to meet a condition for making the high level ofthe output node equal to VDD, it is necessary to increase the potentialat the gate electrode of the n-channel TFT 1001 to a level higher than(VDD+V thN).

According to the present invention, therefore, the following measure isadopted. A capacitor 1003 is provided between the gate and the source ofan n-channel TFT 1001, as shown in FIG. 10B. When the n-channel TFT 1001has a potential at the gate electrode such as to be in a floating state,the potential at the output node is increased. With the increase in thepotential at the output node, the potential at the gate electrode of then-channel TFT 1001 is increased by the function of capacitive couplingthrough the capacitor 1003. By using this effect, it is possible toincrease the potential at the gate electrode of the n-channel TFT 1001to a level higher than VDD (more accurately, higher than (VDD+V thN)).Thus, it is possible to pull up the potential at the output nodesufficiently close to VDD.

A capacitor produced as a parasitic capacitance between the gate and thesource of the TFT 1001 may be used as the capacitor 1003 shown in FIG.10B, or a capacitor portion may be actually fabricated. If a capacitorportion is independently fabricated, a simple manufacturing process ispreferably used in which two of an active layer material, a gatematerial and a wiring material are used and an insulating layer isinterposed between them. However, a capacitor portion may be fabricatedby using other materials. In a case where an active layer is used, it isdesirable to reduce the resistance of the active layer, for example, byadding an impurity to the material of the active layer.

Described hereinafter is the structure of the present invention.

A pulse output circuit according to the present invention comprisesfirst to third transistors, first to third signal input sections, asignal output section, and a power supply, and the pulse output circuitis characterized in that:

the first to third transistors are of the same conductivity type;

a gate electrode of the first transistor is electrically connected tothe first signal input section;

a first electrode of the first transistor is electrically connected tothe second signal input section;

a second electrode of the first transistor is electrically connected toa gate electrode of the second transistor;

a first electrode of the second transistor is electrically connected tothe third signal input section;

a second electrode of the second transistor is electrically connected tothe signal output section;

a gate electrode of the third transistor is electrically connected tothe first signal input section;

a first electrode of the third transistor is electrically connected tothe power supply; and

a second electrode of the third transistor is electrically connected tothe signal output section.

A pulse output circuit according to the present invention comprisesfirst to third transistors, first to fourth signal input sections, asignal output section, a power supply, and an input change circuit, andthe pulse output circuit is characterized in that:

the first to third transistors are of the same conductivity type;

a gate electrode of the first-transistor is electrically connected tothe first signal input section;

a first electrode of the first transistor is electrically connected tothe input change circuit;

the input change circuit is electrically connected to the second signalinput section and to the third signal input section;

a second electrode of the first transistor is electrically connected toa gate electrode of the second transistor;

a first electrode of the second transistor is electrically connected tothe fourth signal input section;

a second electrode of the second transistor is electrically connected tothe signal output section;

a gate electrode of the third transistor is electrically connected tothe first signal input section;

a first electrode of the third transistor is electrically connected tothe power supply; and

a second electrode of the third transistor is electrically connected tothe signal output section.

A pulse output circuit according to the present invention comprisesfirst to third transistors, first to fourth signal input sections, asignal output section, a power supply, and an input change circuit, andthe pulse output circuit is characterized in that:

the first to third transistors are of the same conductivity type;

a gate electrode of the first transistor is electrically connected tothe first signal input section;

a first electrode of the first transistor is electrically connected tothe input change circuit;

the input change circuit is electrically connected to the second signalinput section and to the third signal input section;

a second electrode of the first transistor is electrically connected toa gate electrode of the second transistor;

a first electrode of the second transistor is electrically connected tothe fourth signal input section;

a second electrode of the second transistor is electrically connected tothe signal output section;

a gate electrode of the third transistor is electrically connected tothe first signal input section;

a first electrode of the third transistor is electrically connected tothe power supply;

a second electrode of the third transistor is electrically connected tothe signal output section;

when the input change circuit is in a first state, conduction isprovided between the first electrode of the first transistor and thesecond signal input section and no conduction is provided between thefirst electrode of the first transistor and the third signal inputsection; and

when the input change circuit is in a second state, conduction isprovided between the first electrode of the first transistor and thethird signal input section and no conduction is provided between thefirst electrode of the first transistor and the second signal inputsection.

A pulse output circuit according to the present invention, characterizedin that the input change circuit has a fourth transistor, a fifthtransistor, a fifth signal input section, and a sixth signal inputsection;

each of the fourth transistor and the fifth transistor is of the sameconductivity type as the first to third transistors;

a gate electrode of the fourth transistor is electrically connected tothe fifth signal input section;

a first electrode of the fourth transistor is electrically connected tothe second signal input section;

a second electrode of the fourth transistor is electrically connected tothe first electrode of the first transistor;

a gate electrode of the fifth transistor is electrically connected tothe sixth signal input section;

a first electrode of the fifth transistor is electrically connected tothe third signal input section;

a second electrode of the fifth transistor is electrically connected tothe first electrode of the first transistor;

when an input change signal is input to the fifth signal input sectionand an inverted input change signal is input to the sixth signal inputsection, the fourth transistor is set in a conducting state and thefifth transistor is set in a nonconducting state; and

when the polarity of the input change signal is reversed and thepolarity of the inverted input change signal is reversed, the fourthtransistor is set in a nonconducting state and the fifth transistor isset in a conducting state.

A pulse output circuit according to the present invention furthercomprises capacitor means between the gate electrode and the firstelectrode of the second transistor or between the gate electrode and thesecond electrode of the second transistor.

According to a pulse output circuit of the present invention, thecapacitor means may be formed between the gate electrode of the secondtransistor and an active layer of the second transistor, or between anytwo of an active layer material, a material forming the gate electrode,and a wiring material.

Employing a pulse output circuit of the present invention, there isprovided a shift register in which sampling pulses are successivelyoutput on the basis of first to fourth clock signals and a start pulse.

A shift register according to the present invention is characterized inthat:

the shift register comprises first to fourth clock signal lines and astart pulse input line;

in the pulse output circuit forming the (4n−3) th stage (n: a naturalnumber, 1≦n), the first signal input section is electrically connectedto the first clock signal line;

the second signal input section is electrically connected to the startpulse input line if n=1, or to the signal output section of the pulseoutput circuit forming the (4n−1) th stage if n=1;

the third signal input section is electrically connected to the thirdclock signal line;

in the pulse output circuit forming the (4n−2) th stage, the firstsignal input section is electrically connected to the second clocksignal line;

the second signal input section is electrically connected to the signaloutput section of the pulse output circuit forming the (4n−3) th stage;

the third signal input section is electrically connected to the fourthclock signal line;

in the pulse output circuit forming the (4n−1) th stage, the firstsignal input section is electrically connected to the third clock signalline;

the second signal input section is electrically connected to the signaloutput section of the pulse output circuit forming the (4n−2) th stage;

the third signal input section is electrically connected to the firstclock signal line;

in the pulse output circuit forming the 4n th stage, the first signalinput section is electrically connected to the fourth clock signal line;

the second signal input section is electrically connected to the signaloutput section of the pulse output circuit forming the (4n−1) th stage;

the third signal input section is electrically connected to the secondclock signal line; and

sampling pulses are successively output on the basis of first to fourthclock signals and a start pulse.

A shift register according to the present invention is characterized inthat:

the shift register comprises first to fourth clock signal lines and astart pulse input line;

in the pulse output circuit forming the (4n−3) th stage (n: a naturalnumber, 1≦n), the first signal input section is electrically connectedto the first clock signal line;

the second signal input section is electrically connected to the startpulse input line if n=1, or to the signal output section of the pulseoutput circuit forming the (4n−1) th stage if n=1;

the third signal input section is electrically connected to one of thestart pulse input line and the signal output section of the pulse outputcircuit forming the (4n−2) th stage; and

the fourth signal input section is electrically connected to the thirdclock signal line,

in the pulse output circuit forming the (4n−2) th stage, the firstsignal input section is electrically connected to the second clocksignal line;

the second signal input section is electrically connected to the signaloutput section of the pulse output circuit forming the (4n−3) th stage;

the third signal input section is electrically connected to one of thestart pulse input line and the signal output section of the pulse outputcircuit forming the (4n−1) th stage; and

the fourth signal input section is electrically connected to the fourthclock signal line,

in the pulse output circuit forming the (4n−1) th stage, the firstsignal input section is electrically connected to the third clock signalline;

the second signal input section is electrically connected to the signaloutput section of the pulse output circuit forming the (4n−2) th stage;

the third signal input section is electrically connected to one of thestart pulse input line and the signal output section of the pulse outputcircuit forming the 4n th stage; and

the fourth signal input section is electrically connected to the firstclock signal line,

in the pulse output circuit forming the 4n th stage, the first signalinput section is electrically connected to the fourth clock signal line;

the second signal input section is electrically connected to the signaloutput section of the pulse output circuit forming the (4n−1) th stage;

the third signal input section is electrically connected to one of thestart pulse input line and the signal output section of the pulse outputcircuit forming the (4n+1) th stage; and

the fourth signal input section is electrically connected to the secondclock signal line, and

sampling pulses are successively output on the basis of first to fourthclock signals and a start pulse.

A pulse output circuit according to the present invention may beconstituted only of a transistor whose conductivity type is an n-channeltype, or only of a transistor whose conductivity type is a p-channeltype.

A shift register according to the present invention may be constitutedonly of a transistor whose conductivity type is an n-channel type, oronly of a transistor whose conductivity type is a p-channel type.

BRIE DESCRIPTION OF THE DRAWINGS

In the accompanying drawings:

FIGS. 1A and 1B are diagrams showing a shift register formed by using apulse output circuit in accordance with the present invention;

FIG. 2 is a timing chart relating to drive of the shift register shownin FIGS. 1A and 1B;

FIGS. 3A and 3B are diagrams showing a shift register to which ascanning direction changing function is added, and which represents anembodiment of the present invention;

FIG. 4 is a timing chart relating to drive of the shift register shownin FIGS. 3A and 3B;

FIG. 5 is a diagram showing a structure of a source signal line drivercircuit in a display device provided in accordance with the presentinvention;

FIGS. 6A, 6B, 6C, and 6D are diagrams showing details of a circuitstructure of a level shifter in the display device provided inaccordance with the present invention;

FIGS. 7A, 7B, and 7C are diagrams showing details of circuit structuresof a NAND circuit, a buffer circuit and a sampling switch in the displaydevice provided in accordance with the present invention;

FIG. 8A through 8G are diagrams showing examples of electronic devicesto which the present invention can be applied;

FIGS. 9A through 9E are diagrams showing structures of a conventionalCMOS inverter and load-type inverters and the waveforms of input andoutput signals relating to the inverters;

FIGS. 10A and 10B are diagrams for explaining the principle of the pulseoutput circuit of the present invention;

FIGS. 11A, 11B, and 11C are diagrams showing a circuit configuration ofa conventional shift register and a timing chart;

FIG. 12 is a diagram showing the entire appearance of the display deviceprovided in accordance with the present invention;

FIGS. 13A and 13B are diagrams showing a shift register formed by usinga pulse output circuit constituted of transistors of a conductivity typedifferent from that in embodiment mode of the present invention;

FIG. 14 is a timing chart relating to drive of the shift register shownin FIGS. 13A and 13B;

FIG. 15 is a diagram showing a TFT size and a capacitance value in atest piece of a fabricated shift register;

FIG. 16 is a diagram showing the results of simulation of the shiftregister shown in FIG. 15; and

FIGS. 17A and 17B are diagrams showing the results of measurements ofthe shift register actually fabricated as shown in FIG. 15.

DESCRIPTION OF THE PREFERRED EMBODIMENTS

FIG. 1A schematically shows a shift register in accordance with thepresent invention. A block 100 in the block diagram of FIG. 1Arepresents a pulse output circuit which forms one stage for outputting asampling pulse. The same pulse output circuits are successivelyconnected to form a plurality of stages constituting the shift registershown in FIG. 1A. The shift register shown in FIG. 1A has first tofourth clock signal lines and a start pulse input line. First to fourthclock signals (CK1 to CK4) are respectively input from the first tofourth clock signal lines, and a start pulse (SP) is input from thestart pulse input line.

FIG. 1B shows the detailed circuit structure of the block 100. A gateelectrode of a TFT 101 and a gate electrode of a TFT 103 are connectedto a first signal input section (CKA). The TFT 101 has an inputelectrode connected to a second signal input section (In) and has anoutput electrode connected to the gate electrode of the TFT 102 and toone end of an electrode of a capacitor 104. The TFT 102 has an inputelectrode connected to a third signal input section (CKB). An outputelectrode of the TFT 102, an output electrode of the TFT 103 and theother end of the capacitor 104 are connected to a signal output section(Out). An input electrode of the TFT 103 is connected to a low-potentialpower supply (VSS).

While the circuit in this embodiment mode of the present invention isformed by using only n-channel TFTs, a similar circuit may be formed byusing only p-channel TFTs.

The clock signal input to the first signal input section (CKA) and theclock signal input to the third signal input section (CKB) are oppositein polarity to each other. The second clock signal has a phase delay of¼ period from the first clock signal, and the third clock signal furtherhas a phase delay of ¼ period from the second clock signal. Further, thefourth clock signal has a phase delay of ¼ period from the third clocksignal. That is, the third clock signal has a phase delay of ½ periodfrom the first clock signal and is equal to a signal obtained byreversing the polarity of the first clock signal. Similarly, the fourthclock signal has a phase delay of ½ period from the second clock signaland is equal to a signal obtained by reversing the polarity of thesecond clock signal.

In the shift register using pulse output circuits each of which isformed as shown in FIG. 1B, and which are successively connected to forma plurality of stages, an output pulse from one stage is input to thesecond signal input section (In) in the subsequent stage. In the firststage, a start pulse is input to the second signal input section (In).

Referring to Table 1, in the (4n−3) th stage (n: a natural number, 1≦n),the first clock signal is input to the first signal input section (CKA)and the third clock signal is input to the third signal input section(CKB). In the (4n−2) th stage (n: a natural number, 1≦n), the secondclock signal is input to the first signal input section (CKA) and thefourth clock signal is input to the third signal input section (CKB). Inthe (4n−1) th stage, the third clock signal is input to the first signalinput section (CKA) and the first clock signal is input to the thirdsignal input section (CKB). In the 4n th stage, the fourth clock signalis input to the first signal input section (CKA) and the first clocksignal is input to the third signal input section (CKB).

TABLE 1 Signal input portion (CKA) Signal input portion (CKB) 4(n-1) thstage Fourth clock signal Second clock signal 4n-3 th stage First clocksignal Third clock signal 4n-2 th stage Second clock signal Fourth clocksignal 4n-1 th stage Third clock signal First clock signal 4n th stageFourth clock signal Second clock signal . . . . . . . . .

That is, the shift register in this embodiment mode of the invention hasa certain number of constitutional units each formed of a portionincluding the pulse output circuits in four consecutive stages. Even ifthe number of stages in which the pulse output circuits are connected issmaller than four, the clock signals are input in the order inaccordance with Table 1.

The operation of the circuits will be described with reference to thetiming chart of FIG. 2. The description will be made by assuming thatthe voltage amplitude of the clock signals and the start pulse is lowlevel/high level=VSS/VDD, and that VSS<VDD.

<1> In the first-stage pulse output circuit, the first clock signal(CK1) is supplied to the gate electrodes of the TFTs 101 and 103 andbecomes high level to turn on the TFTs 101 and 103. At this stage, sinceno start pulse (SP) has been input, the potential at the gate electrodeof the TFT 102 is low level and the potential at the signal outputsection (Out) is settled at low level.<2> When a start pulse (SP) input from the signal input section (In)thereafter becomes high level, the potential at the gate electrode ofthe TFT 102 is increased to (VDD−V thN) to be thereafter maintained in afloating state. The TFT 102 is thus turned on. At this point, however,the third clock signal (CK3) input to the signal input section (CKB) islow level and the potential at the signal output section (Out) is notchanged.<3> Subsequently, the first clock signal (CK1) becomes low level to turnoff the TFTs 101 and 103. Simultaneously, the third clock signal (CK3)becomes high level. Since the TFT 102 has already been turned on, thepotential at the signal output section (Out) is increased. The potentialat the gate electrode of the TFT 102, which is maintained in thefloating state at (VDD−V thN) since the TFT 101 has been turned on, isfurther increased from (VDD−V thN) to a level higher than (VDD+V thN) bythe function of the capacitor 104, as the potential at the signal outputsection (Out) is increased. Therefore, when the potential at the signaloutput section (Out) becomes high level, it is equal to VDD.<4> The start pulse (SP) then becomes low level. Subsequently, when thefirst clock signal (CK1) again becomes high level, the TFTs 101 and 103are turned on, the potential at the gate electrode of the TFT 102becomes low level, and the TFT 102 is thus turned off. Because the TFT103 is turned on, the potential at the signal output section (Out)becomes low level.

The circuits in the first to final stages successively operate asdescribed above to output sampling pulses. The shift register formed byusing the pulse output circuit of the present invention is formed onlyof TFTs of one conductivity type but can output pulses of a normalamplitude by avoiding attenuation of the amplitude of the output pulsesdue to the threshold value of the TFTs. Even during the period duringwhich no sampling pulse is output from each stage, the TFT 103 is turnedon each time the clock signal input from the signal input section (CKA)becomes high level, thereby settling the signal output section (Out)potential at low level. The signal output section is not floated for along time. Therefore, the shift register can be used in a circuit of acomparatively low driving frequency, e.g., a gate signal line drivercircuit.

Embodiments of the present invention will be described below.

Embodiment 1

FIG. 3A shows an example of a shift register arranged in such a mannerthat a scanning direction inverting function is added to the shiftregister described above in the description of the embodiment mode ofthe present invention. The shift register of this embodiment usesadditional input signals: an input change signal (LR) and an invertedinput change signal (RL) other than those used in the circuit shown inFIG. 1A.

FIG. 3B shows details of the configuration of the pulse output circuitcorresponding to one stage represented by a block 300 in FIG. 3A. Theportion of the pulse output circuit constituted by TFT's 301 to 303 anda capacitor 304 is the same as the circuit shown in FIG. 1B, and thepulse output circuit of this embodiment has an input change circuit 310constituted by a switch formed of TFTs 305 and 306, a fifth signal inputsection, and a sixth signal input section.

Each of output electrodes of TFTs 305 and 306 is connected to an inputelectrode of TFT 301. TFT 305 has an input electrode connected to asecond signal input section (InL) and has a gate electrode electricallyconnected to the fifth signal input section (L). TFT 306 has an inputelectrode connected to a third signal input section (InR) and has a gateelectrode electrically connected to the sixth signal input section (R).Input change signal (LR) is input to the fifth signal input section (L),while inverted input change signal (RL) is input to the sixth signalinput section (R). Each of LR and RL exclusively has a high level or alow level in relation to each other. Correspondingly, the input changecircuit 310 in this embodiment changes between two states describedbelow.

Firstly, when LR and RL are high level and low level, respectively, TFT305 is turned on and TFT 306 is turned off. A sampling pulse suppliedfrom the preceding stage through the second signal input section (InL)is thus applied to the input electrode of TFT 301. Secondly, when LR andRL are low level and high level, respectively, TFT 305 is turned off andTFT 306 is turned on. A sampling pulse supplied from the preceding stagethrough the third signal input section (InR) is thus applied to theinput electrode of TFT 301.

In the shift register shown in FIG. 3A, sampling pulses are output inthe order of the first stage, the second stage, . . . , and the finalstage when LR and RL are high level and low level, respectively, andsampling pulses are output in the order of the final stage, . . . , thesecond stage, and the first stage when LR and RL are low level and highlevel, respectively.

To change the scanning direction, it is necessary to change timing ofinputting of the clock signals. The timing shown in the timing chart ofFIG. 2 is for scanning in the normal direction. The timing chart of FIG.4 shows timing for scanning in the reverse direction. The clock signalsare input in the order reverse to that shown in FIG. 2. That is, thethird clock signal is input with a ¼ period delay from the fourth clocksignal, the second clock signal is input with a ¼ period delay from thethird clock signal, and the first clock signal is input with a ¼ delayfrom the second clock signal. The start pulse input timing is determineddepending upon the number of stages formed by the pulse output circuitsused in the shift register, i.e., which clock signal the pulse outputcircuit to first output a sampling pulse is driven with. In the exampleof the timing shown in FIG. 4, the fourth clock signal is input to thesignal input section (CKA) of the end pulse output circuit, and thesecond clock signal is input to the signal input section (CKB).

Embodiment 2

An example of a display device fabricated by using only TFTs of onepolarity will be described.

FIG. 12 is a diagram schematically showing the entire display device. Asource signal line driver circuit 1201, a gate signal line drivercircuit 1202, and a pixel portion 1203 are formed integrally with eachother on a substrate 1200. A section of the pixel portion 1203 shown ina frame 1210 indicated by the dotted line is a segment for forming onepixel. The example of the pixel shown in FIG. 12 is a pixel of a liquidcrystal display device. ON/OFF control of each pixel is performed byusing one TFT in the pixel (hereinafter referred to as “pixel TFT”) whencharge is applied to one electrode of the liquid crystal device. Signals(clock signals, a start pulse, etc.) for driving the source signal linedriver circuit 1201 and the gate signal line driver circuit 1202 areexternally supplied via a flexible printed circuit (FPC) 1204.

The substrate having the pixel TFT and the driver circuits may bemanufactured in accordance with a known method, for example, asdisclosed in U.S. Pat. No. 5,889,291 issued to Koyama et al. Also, it ispossible to crystallize a semiconductor film for an active layer of theTFTs by utilizing a metal element for promoting crystallization althoughother known methods can be used for crystallization. Such a method ofusing the metal element is disclosed, for example, in U.S. Pat. No.5,643,826 issued to Ohtani et al. The entire disclosures of these U.S.Pat. Nos. 5,889,291 and 5,643,826 are incorporated herein by reference.

FIG. 5 is a diagram showing the entire structure of the source signalline driver circuit 1201 in the display device shown in FIG. 12. Thesource signal line driver circuit has a clock signal level shifter 501,a start pulse level shifter 502, a pulse output circuits 503constituting a shift register, a NAND circuit 504, a buffer 505, and asampling switch 506. The signals externally supplied are first to fourthclock signals (CK1 to CK4), a start pulse (SP), an input change signal(LR), an inverted input change signal (RL), and analog video signals(Video 1 to Video 12). The first to fourth clock signals (CK1 to CK4)and the start pulse (SP) undergo amplitude conversion in the levelshifter immediately after being externally supplied as low-voltageamplitude signals. These signals are thus converted into high-voltageamplitude signals to be input to the driver circuit. In the sourcesignal line driver circuit in the display device of this embodiment,analog signals corresponding to twelve source signal lines aresimultaneously sampled by driving the sampling switch 506 by means of asampling pulse output from the pulse output circuit forming one stage inthe shift register.

FIG. 6A shows the structure of the clock signal level shifter 501. Inthe clock signal level shifter 501, clock signals opposite in polarityto each other are paired (CK1 and CK3, or CK2 and CK4) and undergoamplitude conversion in a pair of one-input-type level shifters arrangedparallel to each other (in Stage 1), and outputs from the level shiftercircuits are used as inverted inputs to following buffer stages (Stage2, Stage 3, Stage 4).

The operation of the circuit shown in FIG. 6A will be described. Threepower supply potentials VSS, VDD1, and VDD2 are used. These potentialsare in a relationship: VSS<VDD1<VDD2. In this embodiment, VSS=0[V],VDD1=5[V], and VDD2=16[V]. Each of TFTs 601, 603, 606, and 608 shown inFIG. 6A is of a double gate structure. However, these TFTs mayalternatively be provided in a single gate structure or in a multigatestructure having three or more gate electrodes. The number of gates isnot particularly limited with respect to the other TFTs.

First clock signal (CK1) having an amplitude of a low level/highlevel=VSS/VDD1 is input from a signal input section (CK in1). When CK1is high level, each of TFTs 602 and 604 is ON, the potential at the gateelectrode of TFT 603 is low level, and TFT 603 is OFF. The ON resistanceof TFT 602 is set to a sufficiently small value relative to that of TFT601 in the design stage. Therefore, a low level appears at node α. WhenCK1 is low level, each of TFTs 602 and 604 is OFF, so that the potentialat the gate electrode of TFT 603 is pulled up toward VDD2 through TFT601 operating in a saturated state. When the potential becomes equal to(VDD2−V thN), TFT 601 is turned off and the gate electrode of TFT 603 isfloated. TFT 603 is thus turned on and the potential at node α is pulledup toward VDD2. With the increase in the potential at node α, thepotential at the gate electrode of TFT 603 in the floating state ispulled up by the function of capacitor 605 to a level higher than VDD2.The potential at the gate electrode of TFT 603 is thus set above (VDD2+VthN), so that the high level appearing at node α becomes equal to VDD2.As a result, the low level of an output signal becomes equal to VSS andthe high level of the output signal becomes equal to VDD2, thuscompleting amplitude conversion.

On the other hand, third clock signal (CK3) also having the amplitudeVSS-VDD1 is input from a signal input section (CK in2). Theone-input-type level shifter constituted by TFTs 606 to 609 andcapacitor 610 operates in the same manner as that described above toperform amplitude conversion, thereby outputting through node β a signalhaving an amplitude of VSS-VDD2. The signal appearing at node α has thepolarity opposite to that of the input CK1, and the signal appearing atnode β has the polarity opposite to that of the input CK3.

In the level shifter used in the display device of this embodiment,buffer stages (Stages 2 to 4) are provided as stages following the levelshifter circuits (Stage 1) in consideration for the load with respect tothe amplitude-converted pulse. The inverter circuit forming each bufferstage is of a two input type requiring an input signal and an invertedsignal of the input signal. The two-input-type inverter circuit is usedfor the purpose of reducing power consumption. In the above-describedlevel shifter circuit, a shoot-through current flows through TFTs 601and 602 between VSS and VDD2 when TFT 602 is ON. The two-input-typeinverter is used to prevent the shoot-through current from flowingduring operation.

In the inverter circuits in Stage 2 shown in FIG. 6A, the signalsupplied to the gate electrode of TFT 611 and the signal supplied to thegate electrode of TFT 612 are opposite in polarity to each other.Therefore, by utilizing the forms of CK1 and CK3 opposite in polarity toeach other, the output signal appearing at node α and the output signalappearing at node β are used as an input and an inverted input to theTFTs.

The operation of the inverter circuits will be described. The operationof one of the two inverter circuits in Stage 2, i.e., the invertercircuit formed of TFTs 611 to 614 and capacitor 615, will be described.The other inverter circuit operates in the same manner.

When the signal supplied to the gate electrode of TFT 611 is high level,TFT 611 is ON and the potential at the gate electrode of TFT 613 ispulled up toward VDD2. When the potential becomes equal to (VDD2−V thN),TFT 611 is turned off and the gate electrode of TFT 613 is floated. Onthe other hand, since the signal supplied to the gate electrodes of TFTs612 and 614 is low level, each of TFTs 612 and 614 is OFF. Since thepotential at the gate electrode of TFT 613 has been pulled up to (VDD2−VthN), TFT 613 is ON and the potential at node γ is pulled up towardVDD2. As in the operation of the above-described level shifter circuit,with the increase in the potential at node γ, the potential at the gateelectrode of TFT 613 in the floating state is pulled up by the functionof the capacitor 615 to a level higher than VDD2. The potential at thegate electrode of TFT 613 is thus set above (VDD2+V thN), so that thehigh level appearing at node γ becomes equal to VDD2.

When the signal supplied to the gate electrode of TFT 611 is low level,TFT 611 is OFF, high level is supplied to the gate electrodes of TFTs612 and 614, and each of TFTs 612 and 614 is ON. Consequently, thepotential at the gate electrode of TFT 613 is low level and the lowlevel appears at node γ.

A pulse is also output to node δ by the same operation. The pulse outputthrough node δ is opposite in polarity to the pulse appearing at node γ.

The same operation is performed in each of Stages 3 and 4 to finallyoutput pulses to signal output sections (3) and (4).

FIG. 6B shows a state of clock signal amplitude conversion. Theamplitude of the input signal is low level/high level=VSS/VDD1 (0 V/5 V)and the amplitude of the output signal is low level/high level=VSS/VDD2(0 V/16 V).

FIG. 6C illustrates the start pulse (SP) level shifter. The start pulseis used without an inverted signal of it. Therefore, an output from aone-input-type level shifter circuit (Stage 1) is input to aone-input-type inverter circuit (Stage 2). Outputs from Stage 1 andStage 2 are used in a two-input-type inverter circuit (Stage 3). Theoperation of the one-input-type level shifter circuit is the same asthat in the case of processing the clock signal. The one-input-typeinverter circuit operates in the same manner as the one-input-type levelshifter circuit with respect to processing therein except that theamplitude of the input signal is low level/high level=VSS/VDD2 and noamplitude conversion is performed between input and output pulses. Thedescription for these circuits will not be repeated.

FIG. 6D shows a state of start pulse amplitude conversion. The amplitudeof the input signal is low level/high level=VSS/VDD1 (0 V/5 V) and theamplitude of the output signal is low level/high level=VSS/VDD2 (0 V/16V), as are those of the clock signal.

FIG. 7A illustrates the two-input-type NAND circuit. The structure ofthe NAND circuit is similar to that of the one-input-type invertercircuit. The difference resides only in that a two-input signal inputsection is provided in place of that in the one-input inverter circuit,TFTs 702 and 703 are provided in series with each other, and TFTs 705and 706 are also provided in series with each other.

When high level is input to each of signal input sections (In1) and(In2), each of TFTs 702, 703, 705, and 706, is turned on, the potentialat the gate electrode of TFT 704 becomes low level, and TFT 704 is thusturned off. As a result, low level appears at a signal output section(Out). When low level is input to both or one of the signal inputsections (In1) and (In2), conduction is not provided between the gateelectrode of TFT 704 and power supply VSS and the potential at the gateelectrode of TFT 704 is therefore pulled up toward VDD2 to turn on TFT704. Further, the potential is increased to a level higher than (VDD+VthN) by the function of capacitor 707, so that high level correspondingto potential VDD2 appears at the signal output section (Out).

FIG. 7B shows the structure of the buffer circuit constituted by aone-input-type inverter circuit (Stage 1) and two-input-type invertercircuits (Stages 2 to 4). The operation of each of one-input-type andtwo-input-type inverter circuits is the same as that in the levelshifter described above. The description for it will not be repeated.

FIG. 7C shows the structure of the sampling switch. A sampling pulse isinput through a signal input section (25) to simultaneously controltwelve TFTs 731 arranged in parallel with each other. Analog videosignals are supplied to input electrodes (1) to (12) of the twelve TFTs731 to write the potentials of the video signals to the source signallines when a sampling pulse is input.

The inverter circuit and the level shifter circuit in the circuitsconstituting the driver circuits of the display device of thisembodiment may be the same as those described in the specification ofthe invention filed in Japanese Patent Application No. 2001-133431 bythe inventors of the present application.

The driver circuits constituting the entire display device including thepixel portion in this embodiment are fabricated by using only TFTs(e.g., n-channel TFTs) of one polarity which is the same as the polarityof the pixel TFTs. Therefore, the ion doping process for impartingp-type conductivity to a semiconductor layer can be removed. Thiscontributes to a reduction in manufacturing cost and to an improvementin yield.

While the TFTs constituting the display device of this embodiment aren-channel TFTs, driver circuits and pixel TFTs may be formed by usingonly p-channel TFTs according to the present invention. In such a case,the ion doping process to be removed is a process for imparting n-typeconductivity to a semiconductor layer. Also, the present invention isapplied not only to liquid crystal display devices but also to any ofsemiconductor devices if the semiconductor device is fabricated byintegrally forming a driver circuit on an insulator.

Embodiment 3

In the embodiment mode of the present invention and the aboveembodiments of the present invention, examples of the circuits formed byusing only n-channel TFTs have been shown. However, similar circuits maybe formed by using only p-channel TFTs and by interchanging the powersupply-potential levels.

FIGS. 13A and 13B illustrate an example of a shift register formed byusing only p-channel TFTs. The structure shown in the block diagram ofFIG. 13A is the same as that of the shift register shown in FIGS. 1A and1B, which is formed by using only n-channel TFTs. A block 1300 in FIG.13A represents a pulse output circuit forming one stage for outputting asampling pulse. The shift register shown in FIG. 13A differs from theshift register formed by using only n-channel TFTs in that the levels ofthe power supply potentials are reversed as shown in FIG. 13B.

FIG. 14 shows a timing chart and output pulses. The operation of eachsection is the same as that in the embodiment mode described above withreference to FIGS. 1 and 2. Therefore detailed description for it willnot be repeated. The pulses shown in FIG. 14 are expressed by reversingthe high and low levels shown in FIG. 2.

Embodiment 4

A test piece of a shift register shown in FIG. 15 is fabricated inaccordance with the present invention. The shift register is formed tohave nine pulse output circuit stages. The channel length/channel widthand the capacitance value of each TFT are shown in FIG. 15.

FIG. 16 shows the results of simulation of this shift register circuit.As operating conditions, the input signal amplitude is set to lowlevel/high level=0 V/10 V and the power supply potentials of the circuitare also set to the same values. In FIG. 16, first clock signal (CK1),start pulse (SP), shift register first stage output (SROut1), shiftregister second stage output (SROut2), shift register third stage output(SROut3), and shift register fourth stage output (SROut4) are shown inthe top to bottom sections of the graph.

FIGS. 17A and 17B show the results of an operation test of the testpiece of the shift register actually fabricated. In FIG. 17A, firstclock signal (CK1), start pulse (SP), shift register first stage output(SROut1), shift register second stage output (SROut2), shift registerthird stage output (SROut3), and shift register fourth stage output(SROut4) are shown in the top to bottom sections of the graph. In FIG.17B, first clock signal (CK1), start pulse (SP), shift register sixthstage output (SROut6), shift register seventh stage output (SROut7),shift register eighth stage output (SROut8), and shift register finalstage output (SROut9) are shown in the top to bottom sections of thegraph. As shown in FIGS. 17A and 17B, a normal operation at the powersupply voltage 10V and at an driving frequency of about 5 MHz wasconfirmed.

Embodiment 5

The present invention can be applied to manufacture of display devicesto be used in various electronic devices. Examples of such electronicdevices are portable information terminals (an electronic notebook, amobile computer, a portable telephone, etc.), a video camera, a digitalcamera, a personal computer, a television set, and a portable telephone,such as those illustrated in FIGS. 8A through 8G.

FIG. 8A illustrates a liquid crystal display (LCD) constituted by a case3001, a stand 3002, a display portion 3003, etc. The present inventioncan be applied to the display portion 3003.

FIG. 8B illustrates a video camera constituted by a main body 3001, adisplay portion 3012, an audio input portion 3013, operating switches3014, a battery 3015, an image receiving portion 3016, etc. The presentinvention can be applied to the display portion 3012.

FIG. 8C illustrates a notebook-type personal computer constituted by amain body 3021, a case 3022, a display portion 3023, a keyboard 3024,etc. The present invention can be applied to the display portion 3023.

FIG. 8D illustrates a portable information terminal constituted by amain body 3031, a stylus 3032, a display portion 3033, operating buttons3034, an external interface 3035, etc. The present invention can beapplied to the display portion 3033.

FIG. 8E illustrates an audio reproduction device, more specifically anaudio device mounted in a motor vehicle and constituted by a main body3041, a display portion 3042, operating switches 3043 and 3044, etc. Thepresent invention can be applied to the display portion 3042. Theinvention may be applied to any of portable or home audio devices otherthan the above-described audio device mounted in a motor vehicle.

FIG. 8F illustrates a digital camera constituted by a main body 3051, adisplay portion (A) 3052, an ocular portion 3053, operating switches3054, a display portion (B) 3055, a battery 3056, etc. The presentinvention can be applied to each of the display portion (A) 3052 and thedisplay portion (B) 3055.

FIG. 8G illustrates a portable telephone constituted by a main body3061, an audio output portion 3062, an audio input portion 3063, adisplay portion 3064, operating switches 3065, an antenna 3066, etc. Thepresent invention can be applied to the display portion 3064.

It is to be noted that the above-described devices of this embodimentare only examples and that the invention is not exclusively applied tothem.

According to the present invention, even in a case where a drivercircuit and a pixel portion of a display device are formed by using onlyTFTs of one conductivity type, output pulses of a normal amplitude canbe obtained without causing attenuation of the amplitude of the outputpulses due to the threshold value of the TFTs. Thus, the number ofmanufacturing steps can be reduced and this effect contributes to areduction in manufacturing cost and to an improvement in yield. Thus,the present invention makes it possible to supply display devices at areduced cost.

1. (canceled)
 2. A display device comprising: a driver circuit includinga first stage, a second stage, and a third stage, wherein each of thefirst stage, the second stage, and the third stage includes a firsttransistor, a second transistor, a third transistor, a capacitor, and apower supply, wherein a gate electrode of the first transistor isdirectly connected to a gate electrode of the third transistor in eachof the first stage, the second stage, and the third stage, wherein afirst electrode of the first transistor in the first stage is directlyconnected to an output of the second stage, wherein a second electrodeof the first transistor is directly connected to a gate electrode of thesecond transistor in each of the first stage, the second stage, and thethird stage, wherein the second electrode of the first transistor isdirectly connected to a first electrode of the capacitor in each of thefirst stage, the second stage, and the third stage, wherein a firstelectrode of the second transistor is directly connected to a firstelectrode of the third transistor in each of the first stage, the secondstage, and the third stage, wherein a second electrode of the thirdtransistor is directly connected to the power supply in each of thefirst stage, the second stage, and the third stage, wherein a secondelectrode of the capacitor in the first stage is directly connected toan input of the third stage, and wherein the first transistor, thesecond transistor, and the third transistor are the same conductivitytype.
 3. The display device according to claim 2, wherein the gateelectrode of the first transistor is electrically connected to a firstsignal input section in each of the first stage, the second stage, andthe third stage.
 4. The display device according to claim 3, wherein asecond electrode of the second transistor is electrically connected to asecond signal input section in each of the first stage, the secondstage, and the third stage, and wherein a clock signal input to thefirst signal input section and a clock signal input to the second signalinput section are opposite in polarity to each other in each of thefirst stage, the second stage, and the third stage.
 5. The displaydevice according to claim 2, wherein the second electrode of thecapacitor is directly connected to the first electrode of the secondtransistor in each of the first stage, the second stage, and the thirdstage.
 6. The display device according to claim 2, wherein the displaydevice is applied to an electronic device selected from the groupconsisting of a liquid crystal display device, a video camera, anotebook-type personal computer, a portable information terminal, anaudio reproduction device, a digital camera and a portable telephone.